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? semiconductor components industries, llc, 2006 july, 2006 ? rev. 3 1 publication order number: mc34261/d mc34261, mc33261 power factor controllers the mc34261/mc33261 are active power factor controllers specifically designed for use as a preconverter in electronic ballast and in off ? line power converter applications. these integrated circuits feature an internal startup timer, a one quadrant multiplier for near unity power factor, zero current detector to ensure critical conduction operation, high gain error amplifier, trimmed internal bandgap reference, current sensing comparator, and a totem pole output ideally suited for driving a power mosfet. also included are protective features consisting of input undervoltage lockout with hysteresis, cycle ? by ? cycle current limiting, and a latch for single pulse metering. these devices are available in dual ? in ? line and surface mount plastic packages. ? internal startup timer ? one quadrant multiplier ? zero current detector ? trimmed 2% internal bandgap reference ? totem pole output ? undervoltage lockout with hysteresis ? low startup and operating current ? pinout equivalent to the sg3561 ? functional equivalent to the tda4817 http://onsemi.com semiconductor technical data power factor controllers pin connections d suffix plastic package case 751 (so ? 8) 8 1 8 1 p suffix plastic package case 626 voltage feedback input 1 2 3 4 8 7 6 5 (top view) compensation multiplier input current sense input v cc drive output gnd zero current detect input device operating temperature range package ordering information mc34261d mc34261p t a = 0 to +70 c so ? 8 plastic dip mc33261d mc33261p so ? 8 plastic dip t a = ? 40 to +85 c simplified block diagram voltage feedback input multiplier, latch, pwm, timer, & logic v ref error amp multiplier undervoltage lockout 2.5v reference zero current detector 5 8 6 7 4 3 2 1 drive output gnd zero current detect input multiplier input compensation v cc current sense input
mc34261, mc33261 http://onsemi.com 2 maximum ratings rating symbol value unit total power supply and zener current (i cc + i z ) 30 ma output current, source or sink (note 1) i o 500 ma current sense, multiplier, and voltage feedback inputs v in ? 1.0 to 10 v zero current detect input high state forward current low state reverse current i in 50 ? 10 ma power dissipation and thermal characteristics p suffix, plastic package case 626 maximum power dissipation @ t a = 70 c thermal resistance, junction ? to ? air d suffix, plastic package case 626 maximum power dissipation @ t a = 70 c thermal resistance, junction ? to ? air p d r ja p d r ja 800 100 450 178 mw c/w mw c/w operating junction temperature t j +150 c operating ambient temperature (note 3) mc34261 mc33261 t a 0 to +70 ? 40 to +85 c storage temperature t stg ? 55 to +150 c electrical characteristics (v cc = 12 v, for typical values t a = 25 c, for min/max values t a is the operating ambient temperature range that applies [note 3], unless otherwise noted.) characteristic symbol min typ max unit error amplifier voltage feedback input threshold t a = 25 c t a = t low to t high (v cc = 12 v to 28 v) v fb 2.465 2.44 2.5 2.535 2.54 v line regulation (v cc = 12 v to 28 v, t a = 25 c) reg line ? 1.0 10 mv input bias current (v fb = 0 v) i ib ? ? 0.3 ? 1.0 a open loop voltage gain a vol 65 85 ? db gain bandwidth product (t a = 25 c) gbw 0.7 1.0 ? mhz output source current (v o = 4.0 v, v fb = 2.3 v) i source 0.25 0.5 0.75 ma output voltage swing high state (i source = 0.2 ma, v fb = 2.3 v) low state (i sink = 0.4 ma, v fb = 2.7 v) v oh v ol 5.0 ? 5.7 2.1 ? 2.44 v multiplier dynamic input voltage range multiplier input (pin 3) compensation (pin 2) v pin 3 v pin 2 0 to 2.5 v fb to (v fb + 1.0) 0 to 3.5 v fb to (v fb + 1.5) ? ? v input bias current (v fb = 0 v) i ib ? ? 0.3 ? 1.0 a multiplier gain (v pin 3 = 0.5 v, v pin 2 = v fb + 1.0 v) (note 2) k 0.4 0.62 0.8 1/v zero current detector input threshold voltage (v in increasing) v th 1.3 1.6 1.8 v hysteresis (v in decreasing) v h 40 110 200 mv input clamp voltage high state (i det = 3.0 ma) low state (i det = ? 3.0 ma) v ih v il 6.1 0.3 6.7 0.7 ? 1.0 v notes: 1. maximum package power dissipation limits must be observed. 3. t low = ? 4 0 c for mc34261 3. t low = ? 40 c for mc33261 t high = +70 c for mc34261 t high = +85 c for mc33261 pin 4 threshold voltage v pin 3 (v pin 2 ? v fb ) 2. k =
mc34261, mc33261 http://onsemi.com 3 electrical characteristics (v cc = 12 v, for typical values t a = 25 c, for min/max values t a is the operating ambient temperature range that applies [note 3], unless otherwise noted.) characteristic symbol min typ max unit current sense comparator input bias current (v pin 4 = 0 v) i ib ? ? 0.5 ? 2.0 a input offset voltage (v pin 2 = 1.1 v, v pin 3 = 0 v) v io ? 3.5 15 mv delay to output t phl (in/out) ? 200 400 ns drive output output voltage (v cc = 12 v) low state (i sink = 20 ma) low state (i sink = 200 ma) high state (i source = 20 ma) high state (i source = 200 ma) v ol v oh ? 1.8 9.8 7.8 0.3 2.4 10.3 8.3 0.8 3.3 ? 8.8 v output voltage (v cc = 30 v) high state (i source = 20 ma, c l = 15 pf) v o(max) 14 16 18 v output voltage rise time (c l = 1.0 nf) t r ? 50 120 ns output voltage fall time (c l = 1.0 nf) t f ? 50 120 ns output voltage with uvlo activated (v cc = 7.0 v, i sink = 1.0 ma) v oh(uvlo) ? 0.2 0.8 v restart timer restart time delay t dly 150 400 ? s undervoltage lockout startup threshold (v cc increasing) v th 9.2 10.0 10.8 v minimum operating voltage after turn ? on (v cc decreasing) v shutdown 7.0 8.0 9.0 v hysteresis v h 1.75 2.0 2.5 v total device power supply current startup (v cc = 7.0 v) operating dynamic operating (50 khz, c l = 1.0 nf) i cc ? ? ? 0.3 7.1 9.0 0.5 12 20 ma power supply zener voltage v z 30 36 ? v notes: 1. maximum package power dissipation limits must be observed. 3. t low = ? 4 0 c for mc34261 3. t low = ? 40 c for mc33261 t high = +70 c for mc34261 t high = +85 c for mc33261 pin 4 threshold voltage v pin 3 (v pin 2 ? v fb ) 2. k = , current sense threshold voltage (v) cs v 1.0 1.5 , current sense threshold voltage (v) vm, multiplier input voltage (v) ?0.5 4.0 figure 1. current sense input threshold versus multiplier input figure 2. current sense input threshold versus multiplier input ?0.12 vm, multiplier input voltage (v) ?0.08 0 0.04 0.08 0.1 2 0 0.5 2.0 2.5 3.0 3.5 ?0.04 cs v 0 3.0 ?0.5 0.16 ?0.02 2.5 2.0 1.5 1.0 0.5 0 0.14 0.12 0.10 0.08 0.06 0.04 0.02 see figure 2
mc34261, mc33261 http://onsemi.com 4 figure 3. voltage feedback input threshold change versus temperature 0 0.5 1.0 1.5 i sink , output sink current (ma) v sat , output saturation voltage (v) figure 4. error amp open loop gain and phase versus frequency gain phase a vol , open loop voltage gain (db) 100 80 60 40 20 ?20 10 f, frequency (hz) 100 1.0 k 10 k 100 k 1.0 m 10 m 0 , excess phase ( c) 120 180 150 figure 5. error amp small signal transient response v fb , voltage feedback threshold change (mv) +4.0 ?55 t a , ambient temperature ( c) ?4.0 ?8.0 ?12 ?16 ?25 0 25 50 75 100 125 0 figure 6. error amp large signal transient response figure 7. error amp output saturation versus sink current ?55 t a , ambient temperature ( c) ?25 0 25 50 75 100 125 figure 8. restart time delay versus temperature t dly , restart time delay ( s) 2.0 0 30 60 90 2.55 v 2.5 v 2.45 v 0.5 s/div 20 mv/div v cc = 12 v a v = ?1.0 t a = 25 c v cc = 12 v a v = ?1.0 t a = 25 c 200 mv/div 1.0 s/div 3.0 v 2.5 v 2.0 v v cc = 12 v pins 1 to 2 v cc = 12 v v o = 3.0 v to 3.5 v r l = 100 k t a = 25 c 5.0 4.0 3.0 2.0 1.0 0 525 475 425 375 325 275 v cc = 12 v v fb = 2.7 v t a = 25 c v cc = 12 v
mc34261, mc33261 http://onsemi.com 5 figure 9. zero current detector input threshold voltage change versus temperature ?55 ?25 0 25 50 75 100 125 t a , ambient temperature ( c) v cc , supply voltage (v) minimum operating threshold (v cc decreasing) figure 10. output saturation voltage versus load current gnd v cc v sat , output saturation voltage (v) 0 80 160 240 320 i o , output load current (ma) source saturation (load to ground) sink saturation (load to v cc ) v cc = 12 v 80 s pulsed load 120 hz rate figure 11. drive output waveform v th , thre s h o ld v o lta g e c han g e ( mv ) ?55 ?25 0 25 50 75 100 125 t a , ambient temperature ( c) v cc = 12 v upper threshold (v in increasing) lower threshold (v in decreasing) figure 12. drive output cross conduction figure 13. supply current versus supply voltage figure 14. undervoltage lockout thresholds versus temperature i cc , supply current (ma) 10 20 30 40 v cc , supply voltage (v) v fb = 0 v current sense = 0 v multiplier = 0 v c l = 1.0 nf f = 50 khz t a = 25 c v cc = 12 v c l = 1.0 nf t a = 25 c v cc = 12 v c l = 15 pf t a = 25 c 5.0 v/div 90 % 100 ma/div 10 % 100 ns/div 100 ns/div i cc , supply current v o , output voltage 12 11 10 9.0 8.0 6.0 7.0 0 ?2.0 ?4.0 ?6.0 2.0 0 4.0 40 20 0 ?20 ?40 16 12 8.0 4.0 0 0 startup threshold (v cc increasing)
mc34261, mc33261 http://onsemi.com 6 functional description introduction most electronic ballasts and switching power supplies use a bridge rectifier and a filter capacitor to derive raw dc voltage from the utility ac line. this simple rectifying circuit draws power from the line when the instantaneous ac voltage exceeds the capacitor?s voltage. this occurs near the line voltage peak and results in a high charge current spike. since power is only taken near the line voltage peaks, the resulting spikes of current are extremely nonsinusoidal with a high content of harmonics. this results in a poor power factor condition where the apparent input power is much higher than the real power. the mc34261, mc33261 are high performance, critical conduction, current mode power factor controllers specifically designed for use in off ? line active preconverters. these devices provide the necessary features required to significantly enhance poor power factor loads by keeping the ac line current sinusoidal and in phase with the line voltage. with proper control of the preconverter, almost any complex load can be made to appear resistive to the ac line, thus significantly reducing the harmonic current content. operating description the mc34261, mc33261 contains many of the building blocks and protection features that are employed in modern high performance current mode power supply controllers. there are, however, two areas where there is a major difference when compared to popular devices such as the uc3842 series. referring to the block diagram in figure 15, note that a multiplier has been added to the current sense loop and that this device does not contain an oscillator. a description of each of the functional blocks is given below. error amplifier a fully compensated error amplifier with access to the inverting input and output is provided. it features a typical dc voltage gain of 85 db, and a unity gain bandwidth of 1.0 mhz with 58 of phase margin (figure 4). the noninverting input is internally biased at 2.5 v 2.0% and is not pinned out. the output voltage of the power factor converter is typically divided down and monitored by the inverting input. the maximum input bias current is ? 1.0 a which can cause an output voltage error that is equal to the product of the input bias current and the value of the upper divider resistor r 2 . the error amp output is internally connected to the multiplier and is pinned out (pin 2) for external loop compensation. typically , the bandwidth is set below 20 hz, so that the error amp output voltage is relatively constant over a given ac line cycle. the output stage consists of a 500 a current source pull ? up with a darlington transistor pull ? down. it is capable of swinging from 2.1 v to 5.7 v, assuring that the multiplier can be driven over its entire dynamic range. multiplier a single quadrant, two input multiplier is the critical element that enables this device to control power factor. the ac haversines are monitored at pin 3 with respect to ground while the error amp output at pin 2 is monitored with respect to the v oltage feedback input threshold. a graph of the multiplier transfer curve is shown in figure 1. note that both inputs are extremely linear over a wide dynamic range, 0 v to 3.2 v for the multiplier input (pin 3), and 2.5 v to 4.0 v for the error amp output (pin 2). the multiplier output controls the current sense comparator threshold (pin 4) as the ac voltage traverses sinusoidally from zero to peak line. this has the effect of forcing the mosfet peak current to track the input line voltage, thus making the preconverter load appear to be resistive. pin 4 threshold 0.62(v pin 2 ? v fb )v pin 3 zero current detector the mc34261 operates as a critical conduction current mode controller, whereby output switch conduction is initiated by the zero current detector and terminated when the peak inductor current reaches the threshold level established by the multiplier output. the zero current detector initiates the next on ? time by setting the rs latch at the instant the inductor current reaches zero. this critical conduction mode of operation has two significant benefits. first, since the mosfet cannot turn on until the inductor current reaches zero, the output rectifier?s reverse recovery time becomes less critical allowing the use of an inexpensive rectifier. second, since there are no deadtime gaps between cycles, the ac line current is continuous thus limiting the peak switch to twice the average input current. the zero current detector indirectly senses the inductor current by monitoring when the auxiliary winding voltage falls below 1.6 v. to prevent false tripping, 110 mv of hysteresis is provided. the zero current detector input is internally protected by two clamps. the upper 6.7 v clamp prevents input overvoltage breakdown while the lower 0.7 v clamp prevents substrate injection. device destruction can result if this input is shorted to ground. an external resistor must be used in series with the auxiliary winding to limit the current through the clamps. current sense comparator and rs latch the current sense comparator rs latch configuration ensures that only a single pulse appears at the drive output during a given cycle. the inductor current is converted to a voltage by inserting a ground referenced sense resistor r 9 in series with the source of output switch q1. this voltage is monitored by the current sense input and compared to the multiplier output voltage. the peak inductor current is controlled by the threshold voltage of pin 4 where: pin 4 threshold r 9 i pk =
mc34261, mc33261 http://onsemi.com 7 with the component values shown in figure 16, the current sense comparator threshold, at the peak of the haversine varies from 1.1 v at 90 vac to 100 mv at 268 vac. the current sense input to drive output propagation delay is typically 200 ns. timer a watchdog timer function was added to the ic to eliminate the need for an external oscillator when used in stand alone applications. the timer provides a means to automatically start or restart the preconverter if the drive output has been off for more than 400 s after the inductor current reaches zero. undervoltage lockout an undervoltage lockout comparator guarantees that the ic is fully functional before enabling the output stage. the positive power supply terminal (v cc ) is monitored by the uvlo comparator with the upper threshold set at 10 v and the lower threshold at 8.0 v (figure 14). in the standby mode, with v cc at 7.0 v, the required supply current is less than 0.5 ma (figure 13). this hysteresis and low startup current allow the implementation of efficient bootstrap startup techniques, making these devices ideally suited for wide input range off line preconverter applications. an internal 36 v clamp has been added from v cc to ground to protect the ic and capacitor c 5 from an overvoltage condition. this feature is desirable if external circuitry is used to delay the startup of the preconverter. output the mc34261/mc33261 contain a single totem pole output stage specifically designed for direct drive of power mosfets. the drive output is capable of up to 500 ma peak current with a typical rise and fall time of 50 ns with a 1.0 nf load. additional internal circuitry has been added to keep the drive output in a sinking mode whenever the undervoltage lockout is active. this characteristic eliminates the need for an external gate pull ? down resistor. the totem pole output has been optimized to minimize cross conduction current during high speed operation. the addition of two 10 resistors, one in series with the source output transistor and one in series with the sink output transistor, reduces the cross conduction current, as shown in figure 12. a 16 v clamp has been incorporated into the output stage to limit the high state v oh . this prevents rupture of the mosfet gate when v cc exceeds 20 v. table 1. design equations notes calculation formula calculate the maximum required output power. required converter output power p o = v o i o calculated at the minimum required ac line for regula- tion. let the efficiency n = 0.95. peak inductor current i l(pk) = 22 p o vac (ll) let the switching cycle t = 20 s. inductance l = 2t 2 v o vac (ll) i l(pk) v o ? vac vac 2 in theory the on ? time t on is constant. in practice t on tends to increase at the ac line zero crossings due to the charge on capacitor c 6 . switch on ? time vac 2 t on = 2 p o l the off ? time t off is greatest at peak ac line and approaches zero at the ac line zero crossings. theta ( ) represents the angle of the ac line voltage. switch off ? time v o ? 1 t off = 2 vac ? sin ? t on the minimum switching frequency occurs at peak ac line and increases as t off decreases. switching frequency f = t on + t off 1 set the current sense threshold v cs to 1.0 v for universal input (85 vac to 265 vac) operation and to 0.5 v for fixed input (92 vac to 138 vac, or 184 to 276 vac) operation. peak switch current r 9 = i l(pk) v cs set the multiplier input voltage v m to 3.0 v at high line. empirically adjust v m for the lowest distortion over the ac line range while guaranteeing startup at minimum line. multiplier input voltage + 1 vac v m = r 7 2 r 3 the i ib r 1 error term can be minimized with a divider current in excess of 100 a. converter output voltage ? i ib r 2 v o = v ref r 2 + 1 r 1 the bandwidth is typically set to 20 hz for minimum output ripple over the ac line haversine. error amplifier bandwidth bw = r 1 r 2 1 r 1 + r 2 2 c 1 the following converter characteristics must be chosen: v o i o vac vac (ll) ? desired output voltage ? ac rms line voltage ? desired output current ? ac rms low line voltage
mc34261, mc33261 http://onsemi.com 8 + + 100 c 4 100 c 5 10v mtp 8n50e q 1 2.2m r 7 figure 15. 80 w power factor controller + + + + + rfi filter r 6 r 4 c 6 d 4 d 3 d 2 d 1 0.01 c 2 330 1.0nf c 3 0.5ma 6.7v zero current detector v o t uvlo v ref error amp current sense comparator rs latch 1.2v 1.6v 36v 2.5v reference 16v 10 drive output 10 timer multiplier delay 92 to 138 vac 1 7.5k r 3 22k r 5 10 100k r 8 1n4934 d 6 11k r 1 1.0m r 2 0.1 r 9 4 7 8 5 3 6 0.68 c 1 2 1 mur130 d 5 r 230v/ 0.35a power factor controller test data ac line input dc output current harmonic distortion (%) v rms p in pf thd 2357v o(pp) v o i o p o n(%) 90 85.6 ? 0.998 2.4 0.11 0.52 1.3 0.67 10.0 230 0.350 80.5 94.0 100 85.1 ? 0.997 5.0 0.13 1.7 2.4 1.4 10.1 230 0.350 80.5 94.6 110 84.8 ? 0.997 5.3 0.12 2.5 2.6 1.5 10.2 230 0.350 80.5 94.9 120 84.5 ? 0.997 5.8 0.12 3.2 2.7 1.4 10.2 230 0.350 80.5 95.3 130 84.2 ? 0.996 6.6 0.12 4.0 2.8 1.5 10.2 230 0.350 80.5 95.6 138 84.1 ? 0.995 7.2 0.13 4.5 3.0 1.6 10.2 230 0.350 80.5 95.7 = coilcraft n2881 ? a primary: 62 turns of # 22 awg secondary: 5 turns of # 22 awg core: coilcraft pt2510, ee 25 gap: 0.072 total for a primary inductance of 320 h = aavid engineering inc. 5903b, or 5930b t heatsink this data was taken with the test set ? up shown in figure 17.
mc34261, mc33261 http://onsemi.com 9 + + 1.6v timer r 180 c 4 100 c 5 10v mtw 14n50e q 1 1.3m r 7 figure 16. 175 w universal input power factor c ontroller + + + + + rfi filter r 6 r 4 c 6 d 4 d 3 d 2 d 1 0.01 c 2 330 1.0nf c 3 0.5ma 6.7v zero current detector v o t uvlo v ref error amp current sense comparator rs latch 1.2v 36v 2.5v reference 16v 10 drive output 10 multiplier delay 85 to 265 vac 1 12k r 3 22k r 5 10 100k r 8 1n4934 d 6 10k r 1 1.6m r 2 0.1 r 9 4 7 8 5 3 6 0.68 c 1 2 1 mur460 d 5 400v/ 0.44a power factor controller test data ac line input dc output current harmonic distortion (%) v rms p in pf thd 2357v o(pp) v o i o p o n(%) 90 187.5 ? 0.998 2.0 0.10 0.98 0.90 0.78 8.0 400.7 0.436 174.7 93.2 120 184.6 ? 0.997 1.8 0.09 1.3 1.3 0.93 8.0 400.7 0.436 174.7 94.6 138 183.6 ? 0.997 2.3 0.05 1.6 1.5 1.0 8.0 400.7 0.436 174.7 95.2 180 181.0 ? 0.995 4.3 0.16 2.5 2.0 1.2 8.0 400.6 0.436 174.7 95.6 240 179.3 ? 0.993 6.0 0.08 3.7 2.7 1.4 8.0 400.6 0.436 174.7 97.4 268 178.6 ? 0.992 6.7 0.16 2.8 3.7 1.7 8.0 400.6 0.436 174.7 97.8 = coilcraft n2880 ? a primary: 78 turns of # 16 awg secondary: 6 turns of # 18 awg core: coilcraft pt4215, ee 42 ? 15 gap: 0.104 total for a primary inductance of 870 h = aavid engineering inc. 5903b t heatsink this data was taken with the test set ? up shown in figure 17.
mc34261, mc33261 http://onsemi.com 10 figure 17. power factor test set ? up 0.005 1.0 0.005 harm freq 11 lo 0.1 o i t 0 to 270 vac output power factor controller circuit earth line neutral 115 vac input rfi filter autoformer 2x step?up isolation transformer lo hi hi v a ainst acf vcf arms vrms pf va w 13 9 7 5 3 2 1 0 voltech ac power analyzer pm 1000 an rfi filter is required for best performance when connecting the preconverter directly to the ac line. commercially available two stage filters such as the delta electronics 03dpcg5 work excellent. the simple single stage test filter shown above can easily be constructed with a common mode transformer. transformer (t) is a coilcraft cmt3?28?2 with 28 mh minimum inductance and a 2.0 a maximum current rating. + 0.5 ma 2 1 figure 18. soft ? start circuit + t soft?start 9000c in f 1.0m to v cc c to v o startup overshoot can be eliminated with the addition of a soft?start circuit. figure 19. error amp compensation 2 c 1 error amp + 10 a r 1 1 6 r 2
mc34261, mc33261 http://onsemi.com 11 figure 20. printed circuit board and component layout (circuits of figures 15 and 16)
mc34261, mc33261 http://onsemi.com 12 outline dimensions p suffix plastic package case 626 ? 05 issue l notes: 1. dimension l to center of lead when formed parallel. 2. package contour optional (round or square corners). 3. dimensioning and tolerancing per ansi y14.5m, 1982. 14 5 8 f note 2 ? a ? ? b ? ? t ? seating plane h j g d k n c l m m a m 0.13 (0.005) b m t dim min max min max inches millimeters a 9.40 10.16 0.370 0.400 b 6.10 6.60 0.240 0.260 c 3.94 4.45 0.155 0.175 d 0.38 0.51 0.015 0.020 f 1.02 1.78 0.040 0.070 g 2.54 bsc 0.100 bsc h 0.76 1.27 0.030 0.050 j 0.20 0.30 0.008 0.012 k 2.92 3.43 0.115 0.135 l 7.62 bsc 0.300 bsc m ??? 10 ??? 10 n 0.76 1.01 0.030 0.040
mc34261, mc33261 http://onsemi.com 13 outline dimensions d suffix plastic package case 751 ? 07 (so ? 8) issue w seating plane 1 4 5 8 n j x 45 k notes: 1. dimensioning and tolerancing per ansi y14.5m, 1982. 2. controlling dimension: millimeter. 3. dimension a and b do not include mold protrusion. 4. maximum mold protrusion 0.15 (0.006) per side. 5. dimension d does not include dambar protrusion. allowable dambar protrusion shall be 0.127 (0.005) total in excess of the d dimension at maximum material condition. a b s d h c 0.10 (0.004) dim a min max min max inches 4.80 5.00 0.189 0.197 millimeters b 3.80 4.00 0.150 0.157 c 1.35 1.75 0.053 0.069 d 0.33 0.51 0.013 0.020 g 1.27 bsc 0.050 bsc h 0.10 0.25 0.004 0.010 j 0.19 0.25 0.007 0.010 k 0.40 1.27 0.016 0.050 m 0 8 0 8 n 0.25 0.50 0.010 0.020 s 5.80 6.20 0.228 0.244 ? x ? ? y ? g m y m 0.25 (0.010) ? z ? y m 0.25 (0.010) z s x s m on semiconductor and are registered trademarks of semiconductor components industries, llc (scillc). scillc reserves the right to mak e changes without further notice to any products herein. scillc makes no warranty, representation or guarantee regarding the suitability of its products for an y particular purpose, nor does scillc assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including wi thout limitation special, consequential or incidental damages. ?typical? parameters which may be provided in scillc data sheets and/or specifications can and do vary in different application s and actual performance may vary over time. all operating parameters, including ?typicals? must be validated for each customer application by customer?s technical experts. scillc does not convey any license under its patent rights nor the rights of others. scillc products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the scillc product could create a sit uation where personal injury or death may occur. should buyer purchase or use scillc products for any such unintended or unauthorized application, buyer shall indemnify and hold scillc and its of ficers, employees, subsidiaries, af filiates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, direct ly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that scillc was negligent regarding the design or manufacture of the part. scillc is an equal opportunity/affirmative action employer. this literature is subject to all applicable copyright laws and is not for resale in any manner. publication ordering information n. american technical support : 800 ? 282 ? 9855 toll free usa/canada europe, middle east and africa technical support: phone: 421 33 790 2910 japan customer focus center phone: 81 ? 3 ? 5773 ? 3850 mc34261/d literature fulfillment : literature distribution center for on semiconductor p.o. box 5163, denver, colorado 80217 usa phone : 303 ? 675 ? 2175 or 800 ? 344 ? 3860 toll free usa/canada fax : 303 ? 675 ? 2176 or 800 ? 344 ? 3867 toll free usa/canada email : orderlit@onsemi.com on semiconductor website : www.onsemi.com order literature : http://www.onsemi.com/orderlit for additional information, please contact your local sales representative

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